View ADP2107_7851097.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

1 amp/1.5 amp/2 am p synchronous, step-down dc-to-dc converters adp2105/adp2106/ADP2107 rev. 0 information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trademarks are the property of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.461.3113 ?2006 analog devices, inc. all rights reserved. features extremely high 97% efficiency ultralow quiescent current: 20 a 1.2 mhz switching frequency 0.1 a shutdown supply current maximum load current: adp2105: 1 a adp2106: 1.5 a ADP2107: 2 a input voltage: 2.7 v to 5.5 v output voltage: 0.8 v to v in maximum duty cycle: 100% smoothly transitions into low dropout (ldo) mode internal synchronous rectifier small 16-lead 4 mm 4 mm lfcsp_vq package optimized for small ceramic output capacitors enable/shutdown logic input undervoltage lockout soft start applications mobile handsets pdas and palmtop computers telecommunication/networking equipment set top boxes audio/video consumer electronics general description the adp2105/adp2106/ADP2107 are low quiescent current, synchronous, step-down dc-to-dc converters in a compact 4 mm 4 mm lfcsp_vq package. at medium-to-high load currents, these devices use a current-mode, constant-frequency pulse width modulation (pwm) control scheme for excellent stability and transient response. to ensure the longest battery life in portable applications, the adp2105/adp2106/ADP2107 use a pulse frequency modulation (pfm) control scheme under light load conditions that reduces switching frequency to save power. the adp2105/adp2106/ADP2107 run from input voltages of 2.7 v to 5.5 v, allowing single li+/li? polymer cell, multiple alkaline/nimh cells, pcmcia, and other standard power sources. the output voltage of adp2105/adp2106/ADP2107-adj is adjustable from 0.8 v to the input voltage, while the adp2105/ adp2106/ADP2107-xx are available in preset output voltage options of 3.3 v, 1.8 v, 1.5 v, and 1.2 v. each of these variations is available in three maximum current levels, 1 a (adp2105), 1.5 a (adp2106), and 2 a (ADP2107). the power switch and synchro- nous rectifier are integrated for minimal external part count and high efficiency. during logic-controlled shutdown, the input is disconnected from the output, and it draws less than 0.1 a from the input source. other key features include undervoltage lockout to prevent deep-battery discharge and programmable soft start to limit inrush current at startup. typical performance characteristics 100 75 0 2000 06079-001 load current (ma) efficiency (%) 95 90 85 80 200 400 600 800 1000 1200 1400 1600 1800 v in =3.3v v in =3.6v v in =5v v out =2.5v figure 1. efficiency vs. load current for the ADP2107 with v out = 2.5 v typical operating circuit ADP2107-adj off en ss lx2 fb pwin1 agnd output voltage = 2.5v comp on pgnd in gnd gnd gnd nc gnd lx1 pwin2 v in v in input voltage = 2.7v to 5.5v 10 f fb 1nf 70k ? 120pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2 h 4.7 f load 0a to 2a 10 f 10 f 10 ? 0.1 f nc = no connect 06079-002 85k ? 40k ? fb figure 2. circuit configur ation of ADP2107 with v out = 2.5 v
adp2105/adp2106/ADP2107 rev. 0 | page 2 of 32 table of contents features .............................................................................................. 1 applications....................................................................................... 1 general description ......................................................................... 1 typical performance characteristics ............................................. 1 typical operating circuit................................................................ 1 revision history ............................................................................... 2 specifications..................................................................................... 3 absolute maximum ratings............................................................ 5 thermal resistance ...................................................................... 5 boundary co ndition.................................................................... 5 esd caution.................................................................................. 5 pin configuration and function descriptions............................. 6 typical performance characteristics ............................................. 7 theory of operation ...................................................................... 12 control scheme .......................................................................... 12 pwm mode operation.............................................................. 12 pfm mode operation................................................................ 12 pulse-skipping threshold ......................................................... 12 100% duty cycle operation (ldo mode) ............................. 12 slope compensation .................................................................. 13 features ........................................................................................ 13 applications information .............................................................. 15 external component selection................................................. 15 setting the output voltage........................................................ 15 inductor selection ...................................................................... 16 output capacitor selection....................................................... 17 input capacitor selection.......................................................... 17 input filter................................................................................... 18 soft start ...................................................................................... 18 loop compensation .................................................................. 18 bode plots.................................................................................... 19 load transient response .......................................................... 20 efficiency considerations ......................................................... 21 thermal considerations............................................................ 21 design example.......................................................................... 22 external component recommendations.................................... 24 circuit board layout recommendations ................................... 26 evaluation board ............................................................................ 27 evaluation board schematic (ADP2107-1.8v)...................... 27 recommended pcb board layout (evaluation board layout)........................................................ 27 application circuits ....................................................................... 29 outline dimensions ....................................................................... 31 ordering guide .......................................................................... 31 revision history 7/06revision 0: initial version
adp2105/adp2106/ADP2107 rev. 0 | page 3 of 32 specifications v in = 3.6 v @ t a = 25c, unless otherwise noted. 1 bold values indicate ?40c t j +125c. table 1. parameter conditions min typ max unit input characteristics input voltage range 2.7 5.5 v undervoltage lockout threshold v in rising 2.2 2.4 2.6 v v in falling 2.0 2.2 2.5 v undervoltage lockout hysteresis 2 200 mv output characteristics output regulation voltage adp210x-3.3, load = 10 ma 3.267 3.3 3.333 v adp210x-3.3, v in = 3.5 v to 5.5 v, no load to full load 3.201 3.3 3.399 v adp210x-1.8, load = 10 ma 1.782 1.8 1.818 v adp210x-1.8, v in = 2.7 v to 5.5 v, no load to full load 1.746 1.8 1.854 v adp210x-1.5, load = 10 ma 1.485 1.5 1.515 v adp210x-1.5, v in = 2.7 v to 5.5 v, no load to full load 1.455 1.5 1.545 v adp210x-1.2, load = 10 ma 1.188 1.2 1.212 v adp210x-1.2, v in = 2.7 v to 5.5 v, no load to full load 1.164 1.2 1.236 v load regulation adp2105 0.4 %/a adp2106 0.5 %/a ADP2107 0.6 %/a line regulation 3 measured in servo loop 0.1 0.3 %/v output voltage range adp210x-adj 0.8 v in v feedback characteristics adp210x-1.2 3 6 a adp210x-1.5 4 8 a adp210x-1.8 5 10 a out_sense bias current adp210x-3.3 10 20 a fb regulation voltage adp210x-adj 0.784 0.8 0.816 v fb bias current adp210x-adj ?0.1 +0.1 a input current characteristics in operating current adp210x-adj, v fb = 0.9 v 20 30 a adp210x-xx, output voltage 10% above regulation voltage 20 30 a in shutdown current v en = 0 v 0.1 1 5 a lx (switch node) characteristics lx on resistance 4 p-channel switch 100 165 m n-channel synchronous rectifier 90 140 m lx leakage current 4 v in = 5.5 v, v lx = 0 v, 5.5 v 0.1 1 5 a lx peak current limit 4 p-channel switch, ADP2107 2.6 2.9 3.3 a p-channel switch, adp2106 2.0 2.25 2.6 a p-channel switch, adp2105 1.3 1.5 1.8 a lx minimum on-time 4 in pwm mode of operation, v in = 5.5 v 100 ns enable characteristics en input high voltage v in = 2.7 v to 5.5 v 2 v en input low voltage v in = 2.7 v to 5.5 v 0.4 v en input leakage current v in = 5.5 v, v en = 0 v, 5.5 v ?1 ?0.1 +1 a oscillator frequency v in = 2.7 v to 5.5 v 1 1.2 1.4 mhz soft start period c ss = 1 nf 750 1000 1200 s
adp2105/adp2106/ADP2107 rev. 0 | page 4 of 32 parameter conditions min typ max unit thermal characteristics thermal shutdown threshold 140 c thermal shutdown hysteresis 40 c compensator transconductance (g m ) 50 a/v adp2105 1.875 a/v adp2106 2.8125 a/v current sense amplifier gain (g cs ) 2 ADP2107 3.625 a/v 1 all limits at temperature extremes are gua ranteed via correlation using standard stat istical quality control (sqc). typical va lues are at t a = 25c. 2 guaranteed by design. 3 the adp2015/adp2106/ADP2107 line re gulation was measured in a serv o loop on the ate that adjusts the feedback voltage to achieve a specific comp voltage. 4 all lx (switch node) characteristics are guaranteed only when the lx1 and lx2 pins are tied together. 5 these specifications are guaranteed from ?40 c to +85 c.
adp2105/adp2106/ADP2107 rev. 0 | page 5 of 32 absolute maximum ratings table 2. parameter rating in, en, ss, comp, out_sense/fb to agnd ?0.3 v to +6 v lx1, lx2 to pgnd ?0.3 v to (v in + 0.3 v) pwin1, pwin2 to pgnd ?0.3 v to +6 v pgnd to agnd ?0.3 v to +0.3 v gnd to agnd ?0.3 v to +0.3 v pwin1, pwin2 to in ?0.3 v to +0.3 v operating junction temperature range ?40c to +125c storage temperature range ?65c to +150c soldering conditions jedec j-std-020 stresses above those listed under absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. thermal resistance ja is specified for the worst-case conditions, that is, a device soldered in a circuit board for surface-mount packages. table 3. thermal resistance package type ja 1 unit 16-lead lfcsp_vq/qfn 40 c/w maximum power dissipation 1 w 1 ja is specified for the worst-case conditions; that is, ja is specified for device soldered in circuit board for surface mount packages. boundary condition natural convection, 4-layer board, exposed pad soldered to the pcb. esd caution esd (electrostatic discharge) sensitive device. electrosta tic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge without detection. although this product features proprietary esd protection circuitry, permanent dama ge may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd pr ecautions are recommended to avoid performance degradation or loss of functionality.
adp2105/adp2106/ADP2107 rev. 0 | page 6 of 32 pin configuration and fu nction descriptions pin 1 indicator nc = no connect 11 pgnd 12 lx2 10 lx1 9pwin2 c o m p 5 s s 6 a g n d 7 n c 8 adp2105/ adp2106/ ADP2107 top view (not to scale) 15 gnd 16 out_sense/fb 14 in 13 pwin1 e n 1 g n d 2 g n d 3 g n d 4 0 6079-003 figure 3. pin configuration table 4. pin function descriptions mnemonic pin o. adp210xxx adp210xad description 1 en en enable input. drive en high to turn on the adp2105/adp2106/ADP2107. drive en low to turn it off and reduce the input current to 0.1 a. 2, 3, 4, 15 gnd gnd test pins. these pins are used by analog devices, inc. for internal testing and are not ground return pins. tie these pins to the agnd plane as close to the adp2105/adp2106/ADP2107 as possible. 5 comp comp feedback loop compensation node. comp is th e output of the internal transconductance error amplifier. place a series rc network from comp to agnd to compensate the converter. see the loop compensation section. 6 ss ss soft start input. place a capacitor from ss to agnd to set the soft start period. a 1 nf capacitor sets a 1 ms soft start period. 7 agnd agnd analog ground. connect the ground of the comp ensation components, soft start capacitor, and the voltage divider on the fb pin to the agnd pin as close as possible to the adp2105/ adp2106/ADP2107. also connect agnd to th e exposed pad of adp2105/adp2106/ADP2107. 8 nc nc no connect. not internally connected. can be connected to other pins or left unconnected. 9, 13 pwin2, pwin1 pwin2, pwin1 power source inputs. the source of the pfet high-side switch. bypass each pwin pin to the nearest pgnd plane with a 4.7 f or greater capacitor as close as possible to the adp2105/adp2106/ ADP2107. see the input capacitor selection section. 10, 12 lx1, lx2 lx1, lx2 switch outputs. the drain of the p-channel power switch and n-channel synchronous rectifier. tie the two lx pins together and connect th e output lc filter between lx and the output voltage. 11 pgnd pgnd power ground. connect the ground return of a ll input and output capacitors to pgnd pin, using a power ground plane as close as po ssible to the adp2105/adp2106/ADP2107. also connect pgnd to the exposed pa d of the adp2105/adp2106/ADP2107. 14 in in adp2105/adp2106/ADP2107 power input. the power source for the adp2105/adp2106/ ADP2107 internal circuitry. connect in and pwin1 with a 10 resistor as close as possible to the adp2105/adp2106/ADP2107. bypass in to agnd with a 0.1 f or greater capacitor. see the input filter section. 16 out_sense fb output voltage sense or feedback input. for fixed output versions, connect out_sense to the output voltage. for adjustable versions, fb is th e input to the error amplifier. drive fb through a resistive voltage divider to set the output voltage. the fb regulation voltage is 0.8 v.
adp2105/adp2106/ADP2107 rev. 0 | page 7 of 32 typical performance characteristics 100 50 1 1000 06079-004 load current (ma) efficiency (%) 10 100 95 90 85 80 75 70 65 60 55 v in =5.5v v in =4.2v v in =3.6v v in =2.7v inductor: sd14, 2.5h dcr: 60m ? t a = 25c figure 4. efficiencyadp2105 (1.2 v output) 100 50 1 1000 06079-052 load current (ma) efficiency (%) 10 100 95 90 85 80 75 70 65 60 55 v in =4.2v v in =5.5v v in =3.6v inductor: cdrh5d18, 4.1 h dcr: 43m ? t a = 25c figure 5. efficiencyadp2105 (3.3 v output) 100 50 1 10000 06079-062 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1000 v in =2.7v v in =3.6v v in =4.2v v in =5.5v inductor: d62lcb, 2h dcr: 28m ? t a = 25c figure 6. efficiencyadp2106 (1.8 v output) 100 50 1 1000 06079-061 load current (ma) efficiency (%) 10 100 95 90 85 80 75 70 65 60 55 v in =2.7v v in =3.6v v in =4.2v v in =5.5v inductor: sd3814, 3.3h dcr: 93m ? t a = 25c figure 7. efficiencyadp2105 (1.8 v output) 100 50 1 10000 06079-008 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1000 v in =5.5v v in =4.2v v in =3.6v v in =2.7v inductor: d62lcb, 2h dcr: 28m ? t a =25c figure 8. efficiencyadp2106 (1.2 v output) 100 50 1 10000 06079-053 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1000 v in =4.2v v in =5.5v v in =3.6v inductor: d62lcb, 3.3h dcr: 47m ? t a = 25c figure 9. efficiencyadp2106 (3.3 v output)
adp2105/adp2106/ADP2107 rev. 0 | page 8 of 32 100 50 1 10000 06079-010 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1000 v in =4.2v v in =5.5v v in =3.6v v in =2.7v inductor: sd12, 1.2h dcr: 37m ? t a =25c figure 10. efficiencyADP2107 (1.2 v) 100 50 1 10000 06079-054 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1000 v in =4.2v v in =5.5v v in =3.6v inductor: cdrh5d28, 2.5h dcr: 13m ? t a = 25c figure 11. efficiencyADP2107 (3.3 v) 1.85 1.75 0.1 10000 06079-064 load current (ma) output voltage (v) 5.5v, ?40c 5.5v, +25c 2.7v, ?40c 2.7v, +25c 2.7v, +125c 3.6v, ?40c 3.6v, +25c 3.6v, +125c 5.5v, +125c 1.83 1.81 1.79 1.77 1 10 100 1000 figure 12. output voltage accuracyADP2107 (1.8 v) 100 50 1 10000 06079-063 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1000 v in =2.7v v in =3.6v v in =4.2v v in =5.5v inductor: d62lcb, 1.5h dcr: 21m ? t a =25c figure 13. efficiencyADP2107 (1.8 v) 1.23 1.17 0.01 10000 06079-082 load current (ma) output voltage (v) 5.5v, ?40c 5.5v, +25c 2.7v, ?40c 2.7v, +25c 2.7v, +125c 3.6v, ?40c 3.6v, +25c 3.6v, +125c 5.5v, +125c 0.1 1 10 100 1000 1.22 1.21 1.20 1.19 1.18 figure 14. output voltage accuracyADP2107 (1.2 v) 3.38 3.22 0.01 10000 06079-081 load current (ma) output voltage (v) 0.1 1 10 100 1000 3.36 3.34 3.32 3.30 3.28 3.26 3.24 5.5v, ?40c 5.5v, +25c 3.6v, ?40c 3.6v, +25c 3.6v, +125c 5.5v, +125c figure 15. output voltage accuracyADP2107 (3.3 v)
adp2105/adp2106/ADP2107 rev. 0 | page 9 of 32 10000 1 0.8 06079-016 input voltage (v) input current (a) 10 100 1000 1.2 1.6 2.0 2.4 2.8 3.2 3.6 4.0 4.4 4.8 5.2 ?40c +125c +25c figure 16. quiescent current vs. input voltage ?40 125 06079-017 temperature (c) feedback voltage (v) ?20 0 20 40 60 80 100 120 0.795 0.796 0.797 0.798 0.799 0.800 0.801 0.802 figure 17. feedback voltage vs. temperature 1.75 1.25 06079-073 2.7 5.7 input voltage (v) peak current limit (a) 1.70 1.65 1.60 1.55 1.50 1.45 1.40 1.35 1.30 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 adp2105 (1a) t a = 25c figure 18. peak current limit of adp2105 120 0 2.7 5.4 06079-018 input voltage (v) sw on resistance (m ? ) 100 80 60 40 20 3.03.33.63.94.24.54.85.1 nmos synchronous rectifier pmos power switch t a = 25c figure 19. switch on resistance vs. input voltage 1260 1190 2.7 5.4 06079-021 input voltage (v) switching frequency (khz) 1250 1240 1230 1220 1210 1200 3.03.33.63.94.24.54.85.1 ?40c +25c +125c figure 20. switching frequency vs. input voltage 2.35 1.85 06079-072 2.7 5.7 input voltage (v) peak current limit (a) 2.30 2.25 2.20 2.15 2.10 2.05 2.00 1.95 1.90 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 adp2106 (1.5a) t a = 25c figure 21. peak current limit of adp2106
adp2105/adp2106/ADP2107 rev. 0 | page 10 of 32 3.00 2.50 06079-071 2.7 5.7 input voltage (v) peak current limit (a) 2.95 2.90 2.85 2.80 2.75 2.70 2.65 2.60 2.55 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 ADP2107 (2a) t a =25c figure 22. peak current limit of ADP2107 150 0 06079-067 2.7 5.7 input voltage (v) pulse skipping threshold current (ma) 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 135 120 105 90 75 60 45 30 15 v out =2.5v v out =1.2v v out =1.8v t a = 25c figure 23. pulse skipping threshold vs. input voltage for adp2106 06079-074 4 3 1 lx node (switch node) output voltage inductor current : 260mv @: 3.26v ch1 1v 45.8% ch4 1a ? ch3 5v m 10s a ch1 1.78v t figure 24. short circuit response at output 135 0 2.7 5.7 06079-066 input voltage (v) pulse skipping threshold current (ma) 120 105 90 75 60 45 30 15 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 v out =1.8v v out =1.2v v out =2.5v t a =25c figure 25. pulse skipping threshold vs. input voltage for adp2105 195 0 06079-068 2.7 5.7 input voltage (v) pulse skipping threshold current (ma) 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 180 165 150 135 120 105 90 75 60 45 30 15 v out =2.5v v out =1.8v v out =1.2v t a =25c figure 26. pulse skipping threshold vs. input voltage for ADP2107 ?40 06079-083 junction temperature (c) switch on resistance (m ? ) ?20 0 20 40 60 80 100 120 0 20 40 60 80 100 120 140 pmos power switch nmos synchronous rectifier figure 27. switch on resistance vs. temperature
adp2105/adp2106/ADP2107 rev. 0 | page 11 of 32 06079-030 ch1 50mv 6% ch4 200ma ? ch3 2v m 2s a ch3 3.88v t 3 4 1 inductor current output voltage (ac-coupled) lx node (switch node) 06079-031 ch1 20mv 17.4% ch4 1a ? ch3 2v m 1s a ch3 3.88v t 3 4 1 lx node (switch node) output voltage (ac-coupled) inductor current figure 28. pfm mode of operation at very light load (10 ma) figure 31. pwm mode of operation at medium/heavy load (1.5 a) 06079-033 ch1 50mv 17.4% ch4 200ma ? ch3 2v m 400ns a ch3 3.88v t 3 4 1 lx node (switch node) output voltage (ac-coupled) inductor current 06079-032 ch1 1v 45% ch4 1a ? ch3 5v m 4s a ch3 1.8v t 3 4 1 inductor current output voltage channel 3 frequency = 336.6khz : 2.86a @: 2.86a lx node (switch node) figure 29. dcm mode of operation at light load (100 ma) figure 32. current limit behavior of ADP2107 (frequency foldback) 06079-034 ch1 20mv 13.4% ch4 1a ? ch3 2v m 2s a ch3 1.84v t 3 4 1 lx node (switch node) output voltage (ac-coupled) inductor current 06079-035 ch1 1v 20.2% ch4 500ma ? ch3 5v m 400s a ch1 1.84v t 3 4 1 enable voltage inductor current output voltage figure 30. minimum off time control at dropout figure 33. startup and shutdown waveform (c ss = 1 nf ss time = 1 ms)
adp2105/adp2106/ADP2107 rev. 0 | page 12 of 32 theory of operation the adp2105/adp2106/ADP2107 are step-down, dc-to-dc converters that use a fixed frequency, peak current-mode architecture with an integrated high-side switch and low-side synchronous rectifier. the high 1.2 mhz switching frequency and tiny 16-lead, 4 mm 4 mm lfcsp_vq package allow for a small step-down dc-to-dc converter solution. the integrated high-side switch (p-channel mosfet) and synchronous rectifier (n-channel mosfet) yield high efficiency at medium-to- heavy loads. light load efficiency is improved by smoothly transitioning to variable frequency pfm mode. the adp2105/adp2106/ADP2107-adj operate with an input voltage from 2.7 v to 5.5 v and regulate an output voltage down to 0.8 v. the adp2105/adp2106/ADP2107 are also available with preset output voltage options of 3.3 v, 1.8 v, 1.5 v, and 1.2 v. control scheme the adp2105/adp2106/ADP2107 operate with a fixed frequency, peak current-mode pwm control architecture at medium-to-high loads for high efficiency, but shift to a variable frequency pfm control scheme at light loads for lower quies- cent current. when operating in fixed frequency pwm mode, the duty cycle of the integrated switches is adjusted to regulate the output voltage, but when operating in pfm mode at light loads, the switching frequency is adjusted to regulate the output voltage. the adp2105/adp2106/ADP2107 operate in the pwm mode only when the load current is greater than the pulse-skipping threshold current. at load currents below this value, the converter smoothly transitions to the pfm mode of operation. pwm mode operation in pwm mode, the adp2105/adp2106/ADP2107 operate at a fixed frequency of 1.2 mhz set by an internal oscillator. at the start of each oscillator cycle, the p-channel mosfet switch is turned on, putting a positive voltage across the inductor. current in the inductor increases until the current sense signal crosses the peak inductor current level that turns off the p-channel mosfet switch and turns on the n-channel mosfet synchro- nous rectifier. this puts a negative voltage across the inductor, causing the inductor current to decrease. the synchronous rectifier stays on for the rest of the cycle, unless the inductor current reaches zero, which causes the zero-crossing comparator to turn off the n-channel mosfet, as well. the peak inductor current is set by the voltage on the comp pin. the comp pin is the output of a transconductance error amplifier that compares the feedback voltage with an internal 0.8 v reference. pfm mode operation the adp2105/adp2106/ADP2107 smoothly transition to the variable frequency pfm mode of operation when the load current decreases below the pulse-skipping threshold current, switching only as necessary to maintain the output voltage within regulation. when the output voltage dips below regulation, the adp2105/ adp2106/ADP2107 enter pwm mode for a few oscillator cycles to increase the output voltage back to regulation. during the wait time between bursts, both power switches are off, and the output capacitor supplies all the load current. because the output voltage dips and recovers occasionally, the output voltage ripple in this mode is larger than the ripple in the pwm mode of operation. pulse-skipping threshold the output current at which the adp2105/adp2106/ADP2107 transition from variable frequency pfm control to fixed frequency pwm control is called the pulse-skipping threshold. the pulse- skipping threshold has been optimized for excellent efficiency over all load currents. the variation of pulse-skipping threshold with input voltage and output voltage is shown in figure 23 , figure 25 , and figure 26 . 100% duty cycle operation (ldo mode) as the input voltage drops, approaching the output voltage, the adp2105/adp2106/ADP2107 smoothly transition to 100% duty cycle, maintaining the p-channel mosfet switch on continu- ously. this allows the adp2105/adp2106/ADP2107 to regulate the output voltage until the drop in input voltage forces the p-channel mosfet switch to enter dropout, as shown in the following equation: v in(min) = i out ( r ds(on) ? p + dcr ind ) + v out(nom) the adp2105/adp2106/ADP2107 achieve 100% duty cycle operation by stretching the p-channel mosfet switch on-time if the inductor current does not reach the peak inductor current level by the end of the clock cycle. once this happens, the oscil- lator remains off until the inductor current reaches the peak inductor current level, at which time the switch is turned off and the synchronous rectifier is turned on for a fixed off-time. at the end of the fixed off-time, another cycle is initiated. as the adp2105/adp2106/ADP2107 approach dropout, the switching frequency decreases gradually to smoothly transition to 100% duty cycle operation.
adp2105/adp2106/ADP2107 rev. 0 | page 13 of 32 slope compensation slope compensation stabilizes the internal current control loop of the adp2105/adp2106/ADP2107 when operating beyond 50% duty cycle to prevent sub-harmonic oscillations. it is imple- mented by summing a fixed scaled voltage ramp to the current sense signal during the on-time of the p-channel mosfet switch. the slope compensation ramp value determines the minimum inductor that can be used to prevent sub-harmonic oscillations at a given output voltage. the slope compensation ramp values for adp2105/adp2106/ADP2107 follow. for more information, see the inductor selection section. for the adp2105: slope compensation ramp value = 0.72 a/s for the adp2106: slope compensation ramp value = 1.07 a/s for the ADP2107: slope compensation ramp value = 1.38 a/s features enable/shutdown drive en high to turn on the adp2105/adp2106/ADP2107. drive en low to turn off the adp2105/adp2106/ADP2107, reducing input current below 0.1 a. to force the adp2105/ adp2106/ADP2107 to automatically start when input power is applied, connect en to in. when shut down, the adp2105/ adp2106/ADP2107 discharge the soft start capacitor, causing a new soft start cycle every time they are re-enabled. synchronous rectification in addition to the p-channel mosfet switch, the adp2105/ adp2106/ADP2107 include an integrated n-channel mosfet synchronous rectifier. the synchronous rectifier improves efficiency, especially at low output voltage, and reduces cost and board space by eliminating the need for an external rectifier. current limit the adp2105/adp2106/ADP2107 have protection circuitry to limit the direction and amount of current flowing through the power switch and synchronous rectifier. the positive current limit on the power switch limits the amount of current that can flow from the input to the output, while the negative current limit on the synchronous rectifier prevents the inductor current from reversing direction and flowing out of the load. short circuit protection the adp2105/adp2106/ADP2107 include frequency foldback to prevent output current run-away on a hard short. when the voltage at the feedback pin falls below 0.3 v, indicating the possi- bility of a hard short at the output, the switching frequency is reduced to 1/4 of the internal oscillator frequency. the reduction in the switching frequency gives more time for the inductor to discharge, preventing a runaway of output current. undervoltage lockout (uvlo) to protect against deep battery discharge, undervoltage lockout circuitry is integrated on the adp2105/adp2106/ADP2107. if the input voltage drops below the 2.2 v uvlo threshold, the adp2105/adp2106/ADP2107 shut down, and both the power switch and synchronous rectifier turn off. once the voltage rises again above the uvlo threshold, the soft start period is initiated, and the part is enabled. thermal protection in the event that the adp2105/adp2106/ADP2107 junction temperatures rise above 140 c, the thermal shutdown circuit turns off the converter. extreme junction temperatures can be the result of high current operation, poor circuit board design, and/or high ambient temperature. a 40 c hysteresis is included so that when thermal shutdown occurs, the adp2105/adp2106/ ADP2107 do not return to operation until the on-chip tempera- ture drops below 100 c. when coming out of thermal shutdown, soft start is initiated. soft start the adp2105/adp2106/ADP2107 include soft start circuitry to limit the output voltage rise time to reduce inrush current at startup. to set the soft start period, connect the soft start capacitor (c ss ) from ss to agnd. when the adp2105/adp2106/ ADP2107 are disabled, or if the input voltage is below the under- voltage lockout threshold, c ss is internally discharged. when the adp2105/adp2106/ADP2107 are enabled, c ss is charged through an internal 0.8 a current source, causing the voltage at ss to rise linearly. the output voltage rises linearly with the voltage at ss.
adp2105/adp2106/ADP2107 rev. 0 | page 14 of 32 1 fb for adp210x-adj (adjustable version) and out_sense for adp210x-xx (fixed version). 14 13 9 in pwin1 pwin2 12 10 lx2 11 pgnd lx1 2 gnd 7 agnd 16 out_sense 1 16 fb 1 6 ss 5 comp 3 gnd 4 gnd 8 nc 15 gnd 1 en soft start reference 0.8v gm error amp for preset voltages options only pwm/ pfm control current limit zero cross comparator thermal shutdown current sense amplifier driver and anti- shoot through slope compensation oscillator 06079-037 figure 34. block diagram of the adp2105/adp2106/ADP2107
adp2105/adp2106/ADP2107 rev. 0 | page 15 of 32 applications information external component selection the external component selection for the adp2105/adp2106/ ADP2107 application circuits shown in figure 35 and figure 36 depend on input voltage, output voltage, and load current requirements. additionally, tradeoffs between performance parameters like efficiency and transient response can be made by varying the choice of external components. setting the output voltage the output voltage of adp2105/adp2106/ADP2107-adj is externally set by a resistive voltage divider from the output voltage to fb. the ratio of the resistive voltage divider sets the output voltage, while the absolute value of those resistors sets the divider string current. for lower divider string currents, the small 10 na (0.1 a maximum) fb bias current should be taken into account when calculating resistor values. the fb bias current can be ignored for a higher divider string current, but this degrades efficiency at very light loads. to limit output voltage accuracy degradation due to fb bias current to less than 0.05% (0.5% maximum), ensure that the divider string current is greater than 20 a. to calculate the desired resistor values, first determine the value of the bottom divider string resistor, r bot , by string fb bot i v r = where: v fb = 0.8 v, the internal reference. i string is the resistor divider string current. off en ss lx2 agnd output voltage = 1.2v, 1.5v, 1.8v, 3.3 v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 2.7v to 5.5v v out c ss r comp c comp 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 l c out load c in2 c in1 10 ? 0.1 f nc = no connect adp2105/ adp2106/ ADP2107 06079-065 v out out_sense pwin1 ingnd figure 35. typical applications circuit for fixed output voltage options (adp2105/adp2106/ADP2107-xx) off en ss lx2 fb pwin1 agnd output voltage =0.8vtov in comp on pgnd in gnd gnd gnd nc gnd lx1 pwin2 v in v in input voltage = 2.7v to 5.5v fb c ss r comp c comp 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 l c out load c in2 c in1 10 ? 0.1 f r top r bot fb nc = no connect adp2105/ adp2106/ ADP2107 06079-038 figure 36. typical applications circuit for adjustable output voltage option (adp2105/adp2106/ADP2107-adj)
adp2105/adp2106/ADP2107 rev. 0 | page 16 of 32 once r bot is determined, calculate the value of the top resistor, r top , by ? ? ? ? ? ? ? = fb fb out bot top v vv rr the adp2105/adp2106/ADP2107-xx (where xx represents the fixed output voltage) include the resistive voltage divider internally, reducing the external circuitry required. connect the out_sense to the output voltage as close as possible to the load for improved load regulation. inductor selection the high switching frequency of adp2105/adp2106/ADP2107 allows for minimal output voltage ripple even with small inductors. the sizing of the inductor is a trade-off between efficiency and transient response. a small inductor leads to larger inductor current ripple that provides excellent transient response but degrades efficiency. due to the high switching frequency of adp2105/adp2106/ADP2107, shielded ferrite core inductors are recommended for their low core losses and low emi. as a guideline, the inductor peak-to-peak current ripple, i l , is typically set to 1/3 of the maximum load current for optimal transient response and efficiency. 3 ) ( )( max load sw in out in out l i lfv vvv i ? = h ) (5.2 )( max load in out in out ideal iv vvv l ? =? where f sw is the switching frequency (1.2 mhz). the adp2105/adp2106/ADP2107 use slope compensation in the current control loop to prevent subharmonic oscillations when operating beyond 50% duty cycle. the fixed slope compen- sation limits the minimum inductor value as a function of output voltage. for the adp2105: l > (1.12 h/v) v out for the adp2106: l > ( 0.83 h/v ) v out for the ADP2107: l > ( 0.66 h/v ) v out also, 4.7 h or larger inductors are not recommended because they may cause instability in discontinuous conduction mode under light load conditions. finally, it is important that the inductor be capable of handling the maximum peak inductor current, i pk , determined by the following equation: ? ? ? ? ? ? + = 2 )( l max load pk i ii ensure that the maximum rms current of the inductor is greater than the maximum load current, and the saturation current of the inductor is greater than the peak current limit of the converter used in the application. table 5. minimum inductor value for common output voltage options for the adp2105 (1 a) v in v out 2.7 v 3.6 v 4.2 v 5.5 v 1.2 v 1.67 h 2.00 h 2.14 h 2.35 h 1.5 v 1.68 h 2.19 h 2.41 h 2.73 h 1.8 v 2.02 h 2.25 h 2.57 h 3.03 h 2.5 v 2.80 h 2.80 h 2.80 h 3.41 h 3.3 v 3.70 h 3.70 h 3.70 h 3.70 h table 6. minimum inductor value for common output voltage options for the adp2106 (1.5 a) v in v out 2.7 v 3.6 v 4.2 v 5.5 v 1.2 v 1.11 h 2.33 h 2.43 h 1.56 h 1.5 v 1.25 h 1.46 h 1.61 h 1.82 h 1.8 v 1.49 h 1.50 h 1.71 h 2.02 h 2.5 v 2.08 h 2.08 h 2.08 h 2.27 h 3.3 v 2.74 h 2.74 h 2.74 h 2.74 h table 7. minimum inductor value for common output voltage options for the ADP2107 (2 a) v in v out 2.7 v 3.6 v 4.2 v 5.5 v 1.2 v 0.83 h 1.00 h 1.07 h 1.17 h 1.5 v 0.99 h 1.09 h 1.21 h 1.36 h 1.8 v 1.19 h 1.19 h 1.29 h 1.51 h 2.5 v 1.65 h 1.65 h 1.65 h 1.70 h 3.3 v 2.18 h 2.18 h 2.18 h 2.18 h table 8. inductor recommendations for the adp2105/ adp2106/ADP2107 vendor small-sized inductors ( < 5 mm 5 mm) large-sized inductors ( > 5 mm 5 mm) sumida cdrh2d14, 3d16, 3d28 cdrh4d18, 4d22, 4d28, 5d18, 6d12 toko 1069as-db3018, 1098as-de2812, 1070as-db3020 d52lc, d518lc, d62lcb coilcraft lps3015, lps4012, do3314 do1605t cooper bussmann sd3110, sd3112, sd3114, sd3118, sd3812, sd3814 sd10, sd12, sd14, sd52
adp2105/adp2106/ADP2107 rev. 0 | page 17 of 32 output capacitor selection the output capacitor selection affects both the output voltage ripple and the loop dynamics of the converter. for a given loop crossover frequency (the frequency at which the loop gain drops to 0 db), the maximum voltage transient excursion (overshoot) is inversely proportional to the value of the output capacitor. therefore, larger output capacitors result in improved load transient response. to minimize the effects of the dc-to-dc converter switching, the crossover frequency of the compensation loop should be less than 1/10 of the switching frequency. higher crossover frequency leads to faster settling time for a load transient response, but it can also cause ringing due to poor phase margin. lower crossover frequency helps to provide stable operation but needs large output capacitors to achieve competitive overshoot specifications. therefore, the optimal crossover frequency for the control loop of adp2105/adp2106/ADP2107 is 80 khz, 1/15 of the switching frequency. for a crossover frequency of 80 khz, figure 37 shows the maximum output voltage excursion during a 1a load transient, as the product of the output voltage and the output capacitor is varied. choose the output capacitor based on the desired load transient response and target output voltage. 18 0 06079-070 15 70 output capacitor output voltage ( c) % overshoot of output voltage 17 16 15 14 13 12 11 10 9 8 7 6 5 4 3 2 1 20 25 30 35 40 45 50 55 60 65 figure 37. % overshoot for a 1 a load transient response vs. output capacitor output voltage for example, if the desired 1a load transient response (overshoot) is 5% for an output voltage of 2.5 v, then from figure 37 output capacitor output voltage = 50 c f20 5.2 c50 = ? capacitor output the adp2105/adp2106/ADP2107 have been designed for operation with small ceramic output capacitors that have low esr and esl, thus comfortably able to meet tight output voltage ripple specifications. x5r or x7r dialectrics are recommended with a voltage rating of 6.3 v or 10 v. y5v and z5u dialectrics are not recommended, due to their poor temperature and dc bias characteristics. table 9 shows a list of recommended mlcc capacitors from murata and taiyo yuden. it is also important, while choosing output capacitors, to account for the loss of capacitance due to output voltage dc bias. figure 38 shows the loss of capacitance due to output voltage dc bias for a few x5r mlcc capacitors from murata. 20 ?100 06079-060 voltage (v dc ) capacitance change (%) 0 ?20 ?40 ?60 ?80 0 246 1 3 2 1 4.7f 0805 x5r murata grm21br61a475k 2 10f 0805 x5r murata grm21br61a106k 3 22f 0805 x5r murata grm21br60j226m figure 38. % drop-in ca pacitance vs. dc bias for ceramic capacitors (information provided by murata corporation) for example, to get 20 f output capacitance at an output voltage of 2.5 v, based on figure 38 , as well as giving some margin for temperature variance, it is suggested that a 22 f and a 10 f capacitor be used in parallel to ensure that the output capacitance is sufficient under all conditions for stable behavior. table 9. recommended input and output capacitor selection for the adp2105/adp2106/ADP2107 vendor capacitor murata taiyo yuden 4.7 f 10 v x5r 0805 grm21br61a475k lmk212bj475kg 10 f 10 v x5r 0805 grm21br61a106k lmk212bj106kg 22 f 6.3 v x5r 0805 grm21br60j226m jmk212bj226mg input capacitor selection the input capacitor reduces input voltage ripple caused by the switch currents on the pwin pins. place the input capacitors as close as possible to the pwin pins. select an input capacitor capable of withstanding the rms input current for the maximum load current in your application. for the adp2105, it is recommended that each pwin pin be bypassed with a 4.7 f or larger input capacitor. for the adp2106, bypass the pwin pins with a 10 f and a 4.7 f capacitor, and for the ADP2107, bypass each pwin pin with a 10 f capacitor. as with the output capacitor, a low esr ceramic capacitor is recommended to minimize input voltage ripple. x5r or x7r dialectrics are recommended, with a voltage rating of 6.3 v or 10 v. y5v and z5u dialectrics are not recommended, due to their poor temperature and dc bias characteristics. refer to table 9 for input capacitor recommendations.
adp2105/adp2106/ADP2107 rev. 0 | page 18 of 32 input filter the in pin is the power source for the adp2105/adp2106/ ADP2107 internal circuitry, including the voltage reference and current sense amplifier that are sensitive to power supply noise. to prevent high frequency switching noise on the pwin pins from corrupting the internal circuitry of the adp2105/adp2106/ ADP2107, a low-pass rc filter should be placed between the in pin and the pwin1 pin. the suggested input filter consists of a small 0.1 f ceramic capacito r placed between in and agnd and a 10 resistor placed between in and pwin1. this forms a 150 khz low-pass filter between pwin1 and in that prevents any high frequency noise on pwin1 from coupling into the in pin. soft start the adp2105/adp2106/ADP2107 include soft start circuitry to limit the output voltage rise time to reduce inrush current at startup. to set the soft start period, connect a soft start capacitor (c ss ) from ss to agnd. the soft start period varies linearly with the size of the soft start capacitor, as shown in the following equation: t ss = c ss 10 9 ms to get a soft start period of 1 ms, a 1 nf capacitor must be connected between ss and agnd. loop compensation the adp2105/adp2106/ADP2107 utilize a transconductance error amplifier to compensate the external voltage loop. the open loop transfer function at angular frequency, s, is given by ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = out ref out comp cs m v v sc sz ggsh )( )( where: v ref is the internal reference voltage (0.8 v). v out is the nominal output voltage. z comp (s) is the impedance of the co mpensation network at the angular frequency, s. c out is the output capacitor. g m is the transconductance of the error amplifier (50 a/v nominal). g cs is the effective transconductance of the current loop. g cs = 1.875 a/v for the adp2105. g cs = 2.8125 a/v for the adp2106. g cs = 3.625 a/v for the ADP2107. the transconductance error ampl ifier drives the compensation network that consists of a resistor (r comp ) and capacitor (c comp ) connected in series to form a pole and a zero, as shown in the following equation: ? ? ? ? ? ? ? ? + = ? ? ? ? ? ? ? ? += comp comp comp comp comp comp sc csr sc rsz 1 1 )( at the crossover frequency, the gain of the open loop transfer function is unity. this yields the following equation for the compensation network impedance at the crossover frequency: ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = ref out out cs m cross cross comp v vc gg f fz )2( )( where: f cross = 80 khz, the crossover frequency of the loop. c out v out is determined from the output capacitor selection section. to ensure that there is sufficient phase margin at the crossover frequency, place the compensator zero at 1/4 of the crossover frequency, as shown in the following equation: 1 4 )2( = ? ? ? ? ? ? comp comp cross cr f solving the above two simultaneous equations yields the value for the compensation resistor and compensation capacitor, as shown in the following equation: ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = ref out out cs m cross comp v vc gg f r )2( 8.0 comp cross comp rf c 2 =
adp2105/adp2106/ADP2107 rev. 0 | page 19 of 32 bode plots 60 ?40 1 300 (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-055 loop gain loop phase phase margin = 48 crossover frequency = 87khz adp2106 output voltage = 1.8v input voltage = 5.5v load current = 1a inductor = 2.2h (lps4012) output capacitor = 22f + 22f compensation resistor = 180k ? compensation capacitor = 56pf notes 1. external components were chosen for a 5% overshoot for a 1a load transient. figure 39. adp2106 bode plot at v in = 5.5 v, v out = 1.8 v and load = 1 a 60 ?40 1 300 (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-056 notes 1. external components were chosen for a 5% overshoot for a 1a load transient. adp2106 phase margin = 52 loop gain loop phase output voltage = 1.8v input voltage = 3.6v load current = 1a inductor = 2.2h (lps4012) output capacitor = 22f + 22f compensation resistor = 180k ? compensation capacitor = 56pf crossover frequency = 83khz figure 40. adp2106 bode plot at v in = 3.6 v, v out = 1.8 v, and load = 1 a 60 ?40 1 300 (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-057 adp2105 notes 1. external components were chosen for a 5% overshoot for a 1a load transient. loop gain loop phase phase margin = 51 crossover frequency = 71khz output voltage = 1.2v input voltage = 3.6v load current = 1a inductor = 3.3h (sd3814) output capacitor = 22f + 22f + 4.7f compensation resistor = 267k ? compensation capacitor = 39pf figure 41. adp2105 bode plot at v in = 3.6 v, v out = 1.2 v, and load = 1 a 60 ?40 1 300 (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-058 adp2105 notes 1. external components were chosen for a 5% overshoot for a 1a load transient. crossover frequency = 79khz phase margin = 49 loop gain loop phase output voltage = 1.2v input voltage = 5.5v load current = 1a inductor = 3.3h (sd3814) output capacitor = 22f + 22f + 4.7f compensation resistor = 267k ? compensation capacitor = 39pf figure 42. adp2105 bode plot at v in = 5.5 v, v out = 1.2 v and load = 1 a 60 ?40 1 300 (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-059 ADP2107 notes 1. external components were chosen for a 10% overshoot for a 1a load transient. phase margin = 65 crossover frequency = 76khz output voltage = 2.5v input voltage = 5v load current = 1a inductor = 2h (d62lcb) output capacitor = 10f + 4.7f compensation resistor = 70k ? compensation capacitor = 120pf loop phase loop gain figure 43. ADP2107 bode plot at v in = 5 v, v out = 2.5 v and load = 1 a 60 ?40 1 300 (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-069 ADP2107 notes 1. external components were chosen for a 10% overshoot for a 1a load transient. loop gain loop phase phase margin = 70 output voltage = 3.3v input voltage = 5v load current = 1a inductor = 2.5h (cdrh5d28) output capacitor = 10f + 4.7f compensation resistor = 70k ? compensation capacitor = 120pf crossover frequency = 67khz figure 44. ADP2107 bode plot at v in = 5 v, v out = 3.3 v, and load = 1 a
adp2105/adp2106/ADP2107 rev. 0 | page 20 of 32 load transient response 06079-075 ch2 50mv~ ch3 1a ch1 2v m 10s a ch3 0.5a 1 3 2 lx node (switch node) output voltage (ac-coupled) output current output capacitor: 22f + 22f + 4.7f inductor: sd14, 2.5h compensation resistor: 270k ? compensation capacitor: 39pf ch2 low ?51mv figure 45. 1 a load transient response for adp2105-1.2 with external components chosen for 5% overshoot 06079-077 ch2 100mv~ ch3 1a ch1 2v m 10s a ch3 0.5a 1 3 2 lx node (switch node) output voltage (ac-coupled) output current output capacitor: 22f + 22f inductor: sd3814, 3.3h compensation resistor: 270k ? compensation capacitor: 39pf ch2 low ?112mv figure 46. 1 a load transient response for adp2105-1.8 with external components chosen for 5% overshoot 06079-079 ch2 100mv~ ch3 1a ch1 2v m 10s a ch3 0.5a 1 3 2 lx node (switch node) output voltage (ac-coupled) output current output capacitor: 22f + 4.7f inductor: cdrh5d18, 4.1h compensation resistor: 270k ? compensation capacitor: 39pf ch2 low ?178mv figure 47. 1 a load transient response for adp2105-3.3 with external components chosen for 5% overshoot 06079-076 ch2 50mv~ ch3 1a ch1 2v m 10s a ch3 0.5a 1 3 2 lx node (switch node) output voltage (ac-coupled) output current output capacitor: 22f + 4.7f inductor: sd14, 2.5h compensation resistor: 135k ? compensation capacitor: 82pf ch2 low ?93mv figure 48. 1 a load transient response for adp2105-1.2 with external components chosen for 10% overshoot 06079-078 ch2 100mv~ ch3 1a ch1 2v m 10s a ch3 0.5a 1 3 2 lx node (switch node) output voltage (ac-coupled) output current output capacitor: 10f + 10f inductor: sd3814, 3.3h compensation resistor: 135k ? compensation capacitor: 82pf ch2 low ?164mv figure 49. 1 a load transient response for adp2105-1.8 with external components chosen for 10% overshoot 06079-080 ch2 200mv~ ch3 1a ch1 2v m 10s a ch3 0.5a 1 3 2 lx node (switch node) output voltage (ac-coupled) output current output capacitor: 10f + 4.7f inductor: cdrh5d18, 4.1h compensation resistor: 135k ? compensation capacitor: 82pf ch2 low ?308mv figure 50. 1 a load transient response for adp2105-3.3 with external components chosen for 10% overshoot
adp2105/adp2106/ADP2107 rev. 0 | page 21 of 32 efficiency considerations efficiency is defined as the ratio of output power to input power. the high efficiency of the adp2105/adp2106/ADP2107 has two distinct advantages. first, only a small amount of power is lost in the dc-to-dc converter package that reduces thermal constraints. in addition, high efficiency delivers the maximum output power for the given input power, extending battery life in portable applications. there are four major sources of power loss in dc-to-dc converters like the adp2105/adp2106/ADP2107. ? power switch conduction losses ? inductor losses ? switching losses ? transition losses power switch conduction losses power switch conduction losses are caused by the flow of output current through the p-channel power switch and the n-channel synchronous rectifier, which have internal resistances (r ds(on) ) associated with them. the amount of power loss can be approxi- mated by p sw ? cond = [ r ds(on) ? p d + r ds(on) ? n (1 ? d )] i out 2 where d = v out /v in . the internal resistance of the power switches increases with temperature but decreases with higher input voltage. figure 19 in the typical performance characteristics section shows the change in r ds(on) vs. input voltage, while figure 27 in the typical performance characteristics section shows the change in r ds(on) vs. temperature for both power devices. inductor losses inductor conduction losses are caused by the flow of current through the inductor, which has an internal resistance (dcr) associated with it. larger sized inductors have smaller dcr, which can improve inductor conduction losses. inductor core losses are related to the magnetic permeability of the core material. because the adp2105/adp2106/ADP2107 are high switching frequency dc-to-dc converters, shielded ferrite core material is recommended for its low core losses and low emi. the total amount of inductor power loss can be calculated by p l = dcr i out 2 + core losses switching losses switching losses are associated with the current drawn by the driver to turn on and turn off the power devices at the switching frequency. each time a power device gate is turned on and turned off, the driver transfers a charge q from the input supply to the gate and then from the gate to ground. the amount of power loss can by calculated by p sw = ( c gate ? p + c gate ? n ) v in 2 f sw where: ( c gate ? p + c gate ? n ) ~ 600 pf. f sw = 1.2 mhz, the switching frequency. transition losses transition losses occur because the p-channel mosfet power switch cannot turn on or turn off instantaneously. at the middle of a lx node transition, the power switch is providing all the inductor current, while the source to drain voltage of the power switch is half the input voltage, resulting in power loss. transition losses increase with load current and input voltage and occur twice for each switching cycle. the amount of power loss can be calculated by sw out in tran ftti v p off on += )( 2 where t on and t off are the rise time and fall time of the lx node, which are approximately 3 ns. thermal considerations in most applications, the adp2105/adp2106/ADP2107 do not dissipate a lot of heat due to their high efficiency. however, in applications with high ambient temperature, low supply voltage, and high duty cycle, the heat dissipated in the package is large enough that it can cause the junction temperature of the die to exceed the maximum junction temperature of 125c. once the junction temperature exceeds 140c, the converter goes into thermal shutdown. it recovers only after the junction temperature has decreased below 100c to prevent any permanent damage. therefore, thermal analysis for the chosen application solution is very important to guarantee reliable performance over all conditions. the junction temperature of the die is the sum of the ambient temperature of the environment and the temperature rise of the package due to the power dissipation, as shown in the following equation: t j = t a + t r where: t j is the junction temperature. t a is the ambient temperature. t r is the rise in temperature of the package due to power dissipation in it.
adp2105/adp2106/ADP2107 rev. 0 | page 22 of 32 the rise in temperature of the package is directly proportional to the power dissipation in the package. the proportionality constant for this relationship is defined as the thermal resistance from the junction of the die to the ambient temperature, as shown in the following equation: t r = ja p d where: t r is the rise in temperature of the package. p d is the power dissipation in the package. ja is the thermal resistance from the junction of the die to the ambient temperature of the package. for example, consider an application where the ADP2107-1.8 is used with an input voltage of 3.6 v and a load current of 2 a. also, assume that the maximum ambient temperature is 85 c. at a load current of 2 a, the most significant contributor of power dissipation in the dc-to-dc converter package is the conduction loss of the power switches. using the graph of switch resistance vs. temperature (see figure 27 ), as well as the equation of power loss given in the power switch conduction losses section, the power dissipation in the package can be calculated by p sw ? cond = [ r ds(on) ? p d + r ds(on) ? n (1 ? d )] i out 2 = [109 m 0.5 + 90 m 0.5] (2 a) 2 ~ 400 mw the ja for the lfcsp_vq package is 40c/w, as shown in table 3 . thus, the rise in temperature of the package due to power dissipation is t r = ja p d = 40c/w 0.40 w = 16c the junction temperature of the converter is t j = t a + t r = 85c + 16c = 101c which is below the maximum junction temperature of 125c. thus, this application operates reliably from a thermal point of view. design example consider an application with the following specifications: input voltage = 3.6 v to 4.2 v. output voltage = 2 v. typical output current = 600 ma. maximum output current = 1.2 a. soft start time = 2 ms. overshoot 100 mv under all load transient conditions. 1. choose the dc-to-dc converter that satisfies the maximum output current requirement. because the maximum output current for this application is 1.2 a, the adp2106 with a maximum output current of 1.5 a is ideal for this application. 2. see whether the output voltage desired is available as a fixed output voltage option. because 2 v is not one of the fixed output voltage options available, choose the adjustable version of adp2106. 3. the first step in external component selection for an adjustable version converter is to calculate the resistance of the resistive voltage divider that sets the output voltage. === k40 20 v8.0 a i v r string fb bot = ? ? ? ? ? ? ? ? ? = ? ? ? ? ? ? ? = k60 v8.0 v8.0v2 k40 fb fb out bot top v vv rr 4. calculate the minimum inductor value as follows: for the adp2106: l > (0.83 h/v) v out ? l > 0.83 h/v 2 v ? l > 1.66 h next, calculate the ideal inductor value that sets the inductor peak-to-peak current ripple, i l , to1/3 of the maximum load current at the maximum input voltage. = ? = h ) (5.2 )( max load in out in out ideal iv vvv l h2.18h 2.12.4 )22.4(25.2 = ? the closest standard inductor value is 2.2 h. the maximum rms current of the inductor should be greater than 1.2 a, and the saturation current of the inductor should be greater than 2 a. one inductor that meets these criteria is the lps4012-2.2 h from coilcraft. 5. choose the output capacitor based on the transient response requirements. the worst-case load transient is 1.2 a, for which the overshoot must be less than 100 mv, which is 5% of the output voltage. therefore, for a 1 a load transient, the overshoot must be less than 4% of the output voltage. for these conditions, figure 37 gives output capacitor output voltage = 60 c f30 v0.2 c60 = ? capacitor output next, taking into account the loss of capacitance due to dc bias, as shown in figure 38 , two 22 f x5r mlcc capacitors from murata (grm21br60j226m) are sufficient for this application.
adp2105/adp2106/ADP2107 rev. 0 | page 23 of 32 6. because the adp2106 is being used in this application, the input capacitors are 10 f and 4.7 f x5r murata capacitors (grm21br61a106k and grm21br61a475k). 7. the input filter consists of a small 0.1 f ceramic capacitor placed between in and agnd and a 10 resistor placed between in and pwin1. 8. choose a soft start capacitor of 2 nf to achieve a soft start time of 2 ms. 9. finally, the compensation resistor and capacitor can be calculated as ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = ref out out cs m cross comp v vc gg f r )2( 8.0 = ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = k215 v8.0 v2f30 v/a8125.2v/a50 khz80)2( 8. 0 pf39 k 215khz80 2 2 = = = comp cross comp rf c
adp2105/adp2106/ADP2107 rev. 0 | page 24 of 32 external component recommendations table 10. recommended external componen ts for popular output voltage options at 80 khz crossover frequency with 10% overshoot for a 1 a load transient (refer to figure 35 and figure 36 ) part v out (v) c in1 1 (f) c in2 2 (f) c out 3 (f) l (h) r comp (k) c comp (pf) r top 4 (k) r bot 5 (k) adp2105-adj 0.9 4.7 4.7 22 + 10 2.0 135 82 5 40 adp2105-adj 1.2 4.7 4.7 22 + 4.7 2.5 135 82 20 40 adp2105-adj 1.5 4.7 4.7 10 + 10 3.0 135 82 35 40 adp2105-adj 1.8 4.7 4.7 10 + 10 3.3 135 82 50 40 adp2105-adj 2.5 4.7 4.7 10 + 4.7 3.6 135 82 85 40 adp2105-adj 3.3 4.7 4.7 10 + 4.7 4.1 135 82 125 40 adp2106-adj 0.9 4.7 10 22 + 10 1.5 90 100 5 40 adp2106-adj 1.2 4.7 10 22 + 4.7 1.8 90 100 20 40 adp2106-adj 1.5 4.7 10 10 + 10 2.0 90 100 35 40 adp2106-adj 1.8 4.7 10 10 + 10 2.2 90 100 50 40 adp2106-adj 2.5 4.7 10 10 + 4.7 2.5 90 100 85 40 adp2106-adj 3.3 4.7 10 10 + 4.7 3.0 90 100 125 40 ADP2107-adj 0.9 10 10 22 + 10 1.2 70 120 5 40 ADP2107-adj 1.2 10 10 22 + 4.7 1.5 70 120 20 40 ADP2107-adj 1.5 10 10 10 + 10 1.5 70 120 35 40 ADP2107-adj 1.8 10 10 10 + 10 1.8 70 120 50 40 ADP2107-adj 2.5 10 10 10 + 4.7 1.8 70 120 85 40 ADP2107-adj 3.3 10 10 10 + 4.7 2.5 70 120 125 40 adp2105-1.2 1.2 4.7 4.7 22 + 4.7 2.5 135 82 - - adp2105-1.5 1.5 4.7 4.7 10 + 10 3.0 135 82 - - adp2105-1.8 1.8 4.7 4.7 10 + 10 3.3 135 82 - - adp2105-3.3 3.3 4.7 4.7 10 + 4.7 4.1 135 82 - - adp2106-1.2 1.2 4.7 10 22 + 4.7 1.8 90 100 - - adp2106-1.5 1.5 4.7 10 10 + 10 2.0 90 100 - - adp2106-1.8 1.8 4.7 10 10 + 10 2.2 90 100 - - adp2106-3.3 3.3 4.7 10 10 + 4.7 3.0 90 100 - - ADP2107-1.2 1.2 10 10 22 + 4.7 1.5 70 120 - - ADP2107-1.5 1.5 10 10 10 + 10 1.5 70 120 - - ADP2107-1.8 1.8 10 10 10 + 10 1.8 70 120 - - ADP2107-3.3 3.3 10 10 10 + 4.7 2.5 70 120 - - 1 4.7 f 0805 x5r 10 v m urataCgrm21br61a475ka73l. 10 f 0805 x5r 10 v murataCgrm21br61a106ke19l. 2 4.7 f 0805 x5r 10 v m urataCgrm21br61a475ka73l. 10 f 0805 x5r 10 v murataCgrm21br61a106ke19l. 3 4.7 f 0805 x5r 10 v m urataCgrm21br61a475ka73l. 10 f 0805 x5r 10 v murataCgrm21br61a106ke19l. 22 f 0805 x5r 6.3 v murataCgrm21br60j226me39l. 4 0.5% accuracy resistor. 5 0.5% accuracy resistor.
adp2105/adp2106/ADP2107 rev. 0 | page 25 of 32 table 11. recommended external componen ts for popular output voltage options at 80 khz crossover frequency with 5% overshoot for a 1 a load transient (refer to figure 35 and figure 36 ) part v out (v) c in1 1 (f) c in2 2 (f) c out 3 (f) l (h) r comp (k) c comp (pf) r top 4 (k) r bot 5 (k) adp2105-adj 0.9 4.7 4.7 22 + 22 + 22 2.0 270 39 5 40 adp2105-adj 1.2 4.7 4.7 22 + 22 + 4.7 2.5 270 39 20 40 adp2105-adj 1.5 4.7 4.7 22 + 22 3.0 270 39 35 40 adp2105-adj 1.8 4.7 4.7 22 + 22 3.3 270 39 50 40 adp2105-adj 2.5 4.7 4.7 22 + 10 3.6 270 39 85 40 adp2105-adj 3.3 4.7 4.7 22 + 4.7 4.1 270 39 125 40 adp2106-adj 0.9 4.7 10 22 + 22 + 22 1.5 180 56 5 40 adp2106-adj 1.2 4.7 10 22 + 22 + 4.7 1.8 180 56 20 40 adp2106-adj 1.5 4.7 10 22 + 22 2.0 180 56 35 40 adp2106-adj 1.8 4.7 10 22 + 22 2.2 180 56 50 40 adp2106-adj 2.5 4.7 10 22 + 10 2.5 180 56 85 40 adp2106-adj 3.3 4.7 10 22 + 4.7 3.0 180 56 125 40 ADP2107-adj 0.9 10 10 22 + 22 + 22 1.2 140 68 5 40 ADP2107-adj 1.2 10 10 22 + 22 + 4.7 1.5 140 68 20 40 ADP2107-adj 1.5 10 10 22 + 22 1.5 140 68 35 40 ADP2107-adj 1.8 10 10 22 + 22 1.8 140 68 50 40 ADP2107-adj 2.5 10 10 22 + 10 1.8 140 68 85 40 ADP2107-adj 3.3 10 10 22 + 4.7 2.5 140 68 125 40 adp2105-1.2 1.2 4.7 4.7 22 + 22 + 4.7 2.5 270 39 - - adp2105-1.5 1.5 4.7 4.7 22 + 22 3.0 270 39 - - adp2105-1.8 1.8 4.7 4.7 22 + 22 3.3 270 39 - - adp2105-3.3 3.3 4.7 4.7 22 + 4.7 4.1 270 39 - - adp2106-1.2 1.2 4.7 10 22 + 22 + 4.7 1.8 180 56 - - adp2106-1.5 1.5 4.7 10 22 + 22 2.0 180 56 - - adp2106-1.8 1.8 4.7 10 22 + 22 2.2 180 56 - - adp2106-3.3 3.3 4.7 10 22 + 4.7 3.0 180 56 - - ADP2107-1.2 1.2 10 10 22 + 22 + 4.7 1.5 140 68 - - ADP2107-1.5 1.5 10 10 22 + 22 1.5 140 68 - - ADP2107-1.8 1.8 10 10 22 + 22 1.8 140 68 - - ADP2107-3.3 3.3 10 10 22 + 4.7 2.5 140 68 - - 1 4.7f 0805 x5r 10v murata C grm21br61a475ka73l 10f 0805 x5r 10v murata C grm21br61a106ke19l 2 4.7f 0805 x5r 10v murata C grm21br61a475ka73l 10f 0805 x5r 10v murata C grm21br61a106ke19l 3 4.7f 0805 x5r 10v murata C grm21br61a475ka73l 10f 0805 x5r 10v murata C grm21br61a106ke19l 22f 0805 x5r 6.3v murata C grm21br60j226me39l 4 0.5% accuracy resistor 5 0.5% accuracy resistor
adp2105/adp2106/ADP2107 rev. 0 | page 26 of 32 circuit board layout recommendations good circuit board layout is essential in obtaining the best performance from the adp2105/adp2106/ADP2107. poor circuit layout degrades the output ripple, as well as the electromagnetic interference (emi) and electromagnetic compatibility (emc) performance. figure 52 and figure 53 show the ideal circuit board layout for the adp2105/adp2106/ADP2107. use this layout to achieve the highest performance. refer to the following guidelines if adjustments to the suggested layout are needed. ? use separate analog and power ground planes. connect the ground reference of sensitive analog circuitry (such as compensation and output voltage divider components) to analog ground; connect the ground reference of power components (such as input and output capacitors) to power ground. in addition, connect both the ground planes to the exposed pad of the adp2105/adp2106/ADP2107. ? for each pwin pin, place an input capacitor as close to the pwin pin as possible and connect the other end to the closest power ground plane. ? place the 0.1 f, 10 low-pass input filter between the in pin and the pwin1 pin, as close to the in pin as possible. ? ensure that the high current loops are as short and as wide as possible. make the high current path from c in through l, c out , and the pgnd plane back to c in as short as possible. to accomplish this, ensure that the input and output capacitors share a common pgnd plane. also, make the high current path from pgnd pin of the adp2105/adp2106/ADP2107 through l and c out back to the pgnd plane as short as possible. to do this, ensure that the pgnd pin of the adp2105/adp2106/ADP2107 is tied to the pgnd plane as close as possible to the input and output capacitors. ? place the feedback resistor divider network as close as possible to the fb pin to prevent noise pickup. try to minimize the length of trace connecting the top of the feedback resistor divider to the output while keeping away from the high current traces and the switch node (lx) that can lead to noise pickup. to reduce noise pickup, place an analog ground plane on either side of the fb trace. for the low fixed voltage options (1.2 v and 1.5 v), poor routing of the out_sense trace can lead to noise pickup, adversely affecting load regulation. this can be fixed by placing a 1 nf bypass capacitor close to the out_sense pin. ? the placement and routing of the compensation components are critical for proper behavior of the adp2105/adp2106/ ADP2107. the compensation components should be placed as close to the comp pin as possible. it is advisable to use 0402-sized compensation compon ents for closer placement, leading to smaller parasitics. surround the compensation components with analog ground plane to prevent noise pickup. also, ensure that the metal layer under the compensation components is the analog ground plane.
adp2105/adp2106/ADP2107 rev. 0 | page 27 of 32 evaluation board evaluation board sc hematic (ADP2107-1.8 ) j1 u1 en vcc input voltage = 2.7v to 5.5v output voltage = 1.8v, 2a v out vin gnd out vcc out 2 1 gnd vcc ADP2107-1.8 en ss lx2 agnd comp pgnd gnd gnd gnd nc paddle lx1 pwin2 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 17 r2 100k ? c6 68pf c5 1nf r1 140k ? c2 10f 1 l1 2 2h c3 22f 1 c4 22f 1 r4 0 ? r5 ns r3 10? c7 0.1f c1 10f 1 nc = no connect 06079-044 1 murata x5r 0805 10 f: grm21br61a106ke19l 22 f: grm21br60j226me39l 2 2 h inductor d62lcb toko out_sense pwin1 ingnd figure 51. evaluation board schematic of the ADP2107-1.8 (bold traces are high current paths) recommended pcb board layout (evaluation board layout) ground ground connect the ground return of all power components such as input and output capacitors to the power ground plane. power ground plane output capacitor output capacitor c out input capacitor input capacitor output v out c in c out c in jumper to enable enable 100k? pull-down v in input place the feedback resistors as close to the fb pin as possible. adp2105/adp2106/ADP2107 r top r bot c ss r comp c comp place the compensation components as close to the comp pin as possible. analog ground plane connect the ground return of all sensitive analog circuitry such as compensation and output voltage divider to the analog ground plane. lx lx pgnd inductor (l) power ground 0 6079-045 figure 52. recommended layout of top layer of adp2105/adp2106/ADP2107
adp2105/adp2106/ADP2107 rev. 0 | page 28 of 32 power ground plane input voltage plane connecting the two pwin pins as close as possible. connect the pgnd pin to the power ground plane as close to the adp2105/adp2106/ADP2107 as possible. connect the exposed pad of the adp2105/adp2106/ADP2107 to a large ground plane to aid power dissipation. feedback trace: this trace connects the top of the resistive voltage divider on the fb pin to the output. place this trace as far away from the lx node and high current traces as possible to prevent noise pickup. v in v in analog ground plane enable gnd gnd 06079-046 v out figure 53. recommended layout of bottom layer of adp2105/adp2106/ADP2107
adp2105/adp2106/ADP2107 rev. 0 | page 29 of 32 application circuits ADP2107-3.3 off en ss lx2 agnd output voltage = 3.3v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 5v 10 f 1 v out v out 1nf 70k ? 120pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2.5 h 2 4.7 f 1 load 0a to 2a 10 f 1 10 f 1 10 ? 0.1 f 1 murata x5r 0805 10 f: grm21br61a106ke19l 4.7 f: grm21br61a475ka73l 2 sumida cdrh5d28: 2.5 h notes 1. nc = no connect. 2. external components were chosen for a 10% overshoot fora1aloadtransient. 06079-047 out_sense pwin1 in gnd figure 54. application circuitv in = 5 v, v out = 3.3 v, load = 0 a to 2 a ADP2107-1.5 off en ss lx2 agnd output voltage = 1.5v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 3.6v 22 f 1 v out v out 1nf 140k ? 68pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 1.5 h 2 22 f 1 load 0a to 2a 10 f 1 10 f 1 10 ? 0.1 f 1 murata x5r 0805 10 f: grm21br61a106ke19l 22 f: grm21br60j226me39l 2 toko d62lcb or coilcraft lps4012 notes 1. nc = no connect. 2. external components were chosen for a 5% overshoot fora1aloadtransient. 06079-048 out_sense pwin1 in gnd figure 55. application circuitv in = 3.6 v, v out = 1.5 v, load = 0 a to 2 a adp2105-1.8 off en ss lx2 agnd output voltage = 1.8v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 2.7v to 4.2v 22 f 1 v out v out 1nf 270k ? 39pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2.7 h 2 22 f 1 load 0a to 1a 4.7 f 1 4.7 f 1 10 ? 0.1 f 1 murata x5r 0805 4.7 f: grm21br61a475ka73l 22 f: grm21br60j226me39l 2 toko 1098as-de2812: 2.7 h notes 1. nc = no connect. 2. external components were chosen for a 5% overshoot fora1aloadtransient. 06079-049 out_sense pwin1 in gnd figure 56. application circuitv in = li-ion battery, v out = 1.8 v, load = 0 a to 1 a
adp2105/adp2106/ADP2107 rev. 0 | page 30 of 32 adp2105-1.2 off en ss lx2 agnd output voltage = 1.2v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 2.7v to 4.2v 22 f 1 v out v out 1nf 135k ? 82pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2.4 h 2 4.7 f 1 load 0a to 1a 4.7 f 1 4.7 f 1 10? 0.1 f 1 murata x5r 0805 4.7 f: grm21br61a475ka73l 22 f: grm21br60j226me39l 2 toko 1069as-db3018hct or toko 1070as-db3020hct notes 1. nc = no connect. 2. external components were chosen for a 10% overshoot for a 1a load transient. 06079-050 out_sense pwin1 in gnd figure 57. application circuitv in = li-ion battery, v out = 1.2 v, load = 0 a to 1 a adp2106-adj off en ss lx2 fb pwin1 agnd output voltage = 2.5v comp on pgnd in gnd gnd gnd nc gnd lx1 pwin2 v in v in input voltage = 5v fb 1nf 180k ? 56pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2.5 h 2 10 f 1 22 f 1 load 0a to 1.5a 4.7 f 1 10 f 1 10? 0.1 f 1 murata x5r 0805 4.7 f: grm21br61a475ka73l 10 f: grm21br61a106ke19l 22 f: grm21br60j226me39l 2 coiltronics sd14: 2.5 h notes 1. nc = no connect. 2. external components were chosen for a 5% overshoot for a 1a load transient. 85k? 40k? fb 06079-051 figure 58. application circuitv in = 5 v, v out = 2.5 v, load = 0 a to 1.5 a
adp2105/adp2106/ADP2107 rev. 0 | page 31 of 32 outline dimensions compliant to jedec standards mo-220-vggc 2 . 2 5 2 . 1 0 s q 1 . 9 5 16 5 13 8 9 12 1 4 1.95 bsc pin 1 indicator top view 4.00 bsc sq 3.75 bsc sq coplanarity 0.08 exposed pa d (bottom view) 12 max 1.00 0.85 0.80 seating plane 0.35 0.30 0.25 0.80 max 0.65 typ 0.05 max 0.02 nom 0.20 ref 0.65 bsc 0.60 max 0.60 max pin 1 indicator 0.25 min 010606-0 0.75 0.60 0.50 figure 59. 16-lead lead frame chip scale package [lfcsp_vq] 4 mm 4 mm body, very thin quad (cp-16-4) dimensions shown in millimeters ordering guide model output current junction temperature range output voltage package description package option adp2105acpz-1.2-r7 1 1 a ?40c to +125c 1.2 v 16-lead lfcsp_vq cp-16-4 adp2105acpz-1.5-r7 1 1 a ?40c to +125c 1.5 v 16-lead lfcsp_vq cp-16-4 adp2105acpz-1.8-r7 1 1 a ?40c to +125c 1.8 v 16-lead lfcsp_vq cp-16-4 adp2105acpz-3.3-r7 1 1 a ?40c to +125c 3.3 v 16-lead lfcsp_vq cp-16-4 adp2105acpz-r7 1 1 a ?40c to +125c adj 16-lead lfcsp_vq cp-16-4 adp2106acpz-1.2-r7 1 1.5 a ?40c to +125c 1.2 v 16-lead lfcsp_vq cp-16-4 adp2106acpz-1.5-r7 1 1.5 a ?40c to +125c 1.5 v 16-lead lfcsp_vq cp-16-4 adp2106acpz-1.8-r7 1 1.5 a ?40c to +125c 1.8 v 16-lead lfcsp_vq cp-16-4 adp2106acpz-3.3-r7 1 1.5 a ?40c to +125c 3.3 v 16-lead lfcsp_vq cp-16-4 adp2106acpz-r7 1 1.5 a ?40c to +125c adj 16-lead lfcsp_vq cp-16-4 ADP2107acpz-1.2-r7 1 2 a ?40c to +125c 1.2 v 16-lead lfcsp_vq cp-16-4 ADP2107acpz-1.5-r7 1 2 a ?40c to +125c 1.5 v 16-lead lfcsp_vq cp-16-4 ADP2107acpz-1.8-r7 1 2 a ?40c to +125c 1.8 v 16-lead lfcsp_vq cp-16-4 ADP2107acpz-3.3-r7 1 2 a ?40c to +125c 3.3 v 16-lead lfcsp_vq cp-16-4 ADP2107acpz-r7 1 2 a ?40c to +125c adj 16-lead lfcsp_vq cp-16-4 adp2105-1.8-eval 1.8 v evaluation board adp2105-eval adjustable, but se t to 2.5 v evaluation board adp2106-1.8-eval 1.8 v evaluation board adp2106-eval adjustable, but se t to 2.5 v evaluation board ADP2107-1.8-eval 1.8 v evaluation board ADP2107-eval adjustable, but se t to 2.5 v evaluation board 1 z = pb-free part.
adp2105/adp2106/ADP2107 rev. 0 | page 32 of 32 notes ?2006 analog devices, inc. all rights reserved. trademarks and registered trademarks are the property of their respective owners. d06079-0-7/06(0)

▲Up To Search▲

Price & Availability of ADP2107

	To Download ADP2107 Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .